Miscellaneous active electrical nonlinear devices – circuits – and – Signal converting – shaping – or generating – Phase shift by less than period of input
Reexamination Certificate
2002-08-12
2004-06-08
Wells, Kenneth B. (Department: 2816)
Miscellaneous active electrical nonlinear devices, circuits, and
Signal converting, shaping, or generating
Phase shift by less than period of input
C327S254000, C327S255000
Reexamination Certificate
active
06747499
ABSTRACT:
The present invention relates to a tunable quadrature phase shifter comprising an input means for inputting an input signal, splitting means for splitting the input signal into two essentionaly orthogonal first and second signals, adding means for adding said first and second signals, subtracting means for subtracting said first and second signals, a first output for outputting a first output signal based on the output signal from said adding means, and a second output for outputting a second output signal based on the output signal from said subtracting means.
Such a phase shifter which provides two output signals in quadrature are used in e.g. mobile communication systems and other radio transmitter and receiver systems where an accurate 90 degrees phase shift is necessary to obtain a sufficient image rejection in the transmitter and to have a correct 90 degrees phase difference between the I (In-phase) and Q (Quadrature-phase) base band phase vector signals in the receiver. In particular, a possible application is the I/Q generation for RC/LC oscillators with large tuning range (“Sonet”/“SDH” applications). Further, such a phase shifter is used in polyphase filters, QUAMs, Low IF/Zero IF receivers as well as Data and Clock Recovery (DCR) and Phase-Looked-Loop (PLL) circuits.
Among the first known techniques for quadrature signal generation is the RC-CR technique shown in FIG.
1
. Here, an input signal vin is shifted by −&pgr;/4 to form a first output signal vo
1
and by +&pgr;/4 to form a second output signal vo
2
. The phase difference between the output signals vo
1
and vo
2
is always &pgr;/2, but the amplitudes of the output signals vo
1
and vo
2
are equal at one frequency fo=1/(2&pgr;RC) only.
After shifting, limiting stages (not shown in
FIG. 1
) can be used, but amplitude limiting becomes difficult in the GHz range unless several stages are connected in cascade. This operation is possible in case only zero crossings of the signal are relevant. Nevertheless, there is always a mismatch in gain and amplitude between both the output signals vo
1
and vo
2
in the two parallel paths. Moreover, due to nonlinear effects, slew-rate (dvin/dt) like AM to PM conversion occurs. When the RC time constant varies with process and temperature, the cutoff frequency at which the amplitudes of both the output signals vo
1
and vo
2
are equal varies, too. Besides, the mismatch between passive components results also in a phase mismatch.
Another conventional method for quadrature generation is the Havens technique according to FIG.
2
. The input signal is splitted into two branches by using a quadrature circuit
2
which has approximately quadrature outputs. The precision of this circuit is not mandatory. These two signals are:
v
1
(t)=A cos (&ohgr;t)
v
2
(
t
)=
A
cos (&ohgr;
t
+&thgr;) (1).
After each of these two signals vo
1
and vo
2
is limited in amplitude by a limiter
4
and
5
, respectively, these two signals are added by an adder
6
and also subtracted by a subtracter
7
. Each of the signals from the outputs of the adder
6
and subtracter
7
are again limited in amplitude by limiters
8
and
9
, respectively, to form the output signals vo
1
and vo
2
. The interesting part comes from the fact that a phase imbalance from &pgr;/2 gives afterwards an amplitude mismatch between the two signals v
1
and v
2
cancelled away by the limiting action. This operation is explained below:
v
1
+
v
2
=
2
A
cos
(
θ
2
)
cos
(
ω
t
+
θ
2
)
v
1
-
v
2
=
2
A
sin
(
θ
2
)
sin
(
ω
t
+
θ
2
)
(
2
)
.
The amplitudes A of the sum and difference signals are equal if the phase shifter has two outputs in quadrature (&thgr;=&pgr;/2). Assuming that in the second signal v
2
there is an amplitude mismatch of magnitude &egr;, the equation for the second signal v
2
reads as follows:
v
2
=(
A
+&egr;) cos (&ohgr;
t
+&thgr;) (3).
The effect of such error is that v
1
+v
2
rotates counterclockwise by &PHgr;
1
and v
1
−v
2
clockwise by &PHgr;
2
. In
FIG. 3
the phasor diagram of the signals is shown. The two situations depicted correspond to the situation when no amplitude errors are present (
FIG. 3
a
) and the situation when amplitude errors are present (
FIG. 3
b
). From
FIG. 3
one can find the phase errors &PHgr;
1
and &PHgr;
2
and the local phase error &PHgr;
1
+&PHgr;
2
under the assumption that the amplitude error &egr; is small when compared with the amplitude A, i.e. &egr;<<A.
The equations for the phase errors &PHgr;
1
and &PHgr;
2
are
tan
(
Φ
1
)
=
ϵ
sin
(
θ
2
)
2
A
cos
(
θ
2
)
+
ϵ
cos
(
θ
2
)
tan
(
Φ
2
)
=
ϵ
cos
(
θ
2
)
2
A
sin
(
θ
2
)
+
ϵ
sin
(
θ
2
)
When
ϵ
<<
A
the
result
is
:
(
4
)
.
Φ1
+
Φ2
≅
ϵ
A
sin
(
θ
)
(
5
)
.
The amplitude mismatch &egr; leads to a phase mismatch. 1% amplitude mismatch generates 0.6° in phase. Although this method is better in terms of robustness to errors, the disadvantage consists in the use of the four limiters
4
,
5
,
8
and
9
which convert amplitude modulation into phase modulation. Another critical disadvantage is that even some amplitude errors are tolerated, the input quadrature generator produces for different frequencies unequal amplitudes. Therefore, when the above described quadrature generation circuit is coupled to oscillators for I/Q processing by tuning the oscillator within an octave for example, the amplitude of the two paths drastically varies.
FIG. 2
shows the closest prior art from which the invention proceeds.
EP 0 707 379 A1 discloses a tunable quadrature phase shifter including two branches each constituted by cascade connection of a filter, an amplifier and a summing circuit, and two cross-connections constituted by amplifiers interconnecting the filter of one branch to the summing circuit of the opposite branch. An accurate 90° phase shift between the two output signals is obtained by controlling the tail currents of the four amplifiers.
WO 92/11704 A1 describes a quadrature signal generator including a phase-locked loop configuration which comprises a voltage control phase-shift network, limiters, an exclusive-OR phase detector, a low phase filter, a differential voltage to current converter and a loop filter. The voltage controlled phase-shift network generates a phase shift for the differential quadrature signals. The exclusive-OR phase detector determines the phase error between the differential quadrature signals. The phase error is related to a voltage control signal which is coupled back to the voltage controlled phased-shift network to maintain a precise 90° phase relationship between the differential quadrature signals.
Due to the control mechanism, both the devices according to EP 0 707 379 A1 and WO 92/11704 A1 require a complex and expensive construction.
Accordingly, it is an object of the present invention to provide a simple construction which avoids the amplitude mismatch and can be used for oscillators with more than one octave frequency tuning.
In order to achieve the above and other objects, according to the present invention, there is provided a tunable quadrature phase shifter comprising an input means for inputting an input signal, splitting means for splitting the input signal into two essentially orthogonal first and second signals, adding means for adding said first and second signals, subtract
Koninklijke Philips Electronics , N.V.
Waxler Aaron
Wells Kenneth B.
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